## A New ZCS High Step-up DC-DC Converter

**Majid Delshad**^{1,}, **Nima rakian**^{1}

^{1}Electrical Department, Khorasgan Branch, Islamic Azad University, Isfahan, Iran

2. Circuit Configuration and Operation Principle of the Proposed Converter

### Abstract

In this paper, a new high step-up PWM soft single switched converter is introduced. The proposed converter does not need any auxiliary switch to provide soft switching condition which causes simplification of control circuit. In this converter, the switch is turned on ZCS condition and turned off at almost ZVS. One of the main advantages of this converter is the possibility of sharing the output power between the magnetic devices and operating at high power levels. The experimental results obtain from the proposed converter verify the theoretical analysis.

### At a glance: Figures

**Keywords:** single switch, ZCS, almost ZVS, PWM, DC-DC converter

*International Transaction of Electrical and Computer Engineers System*, 2013 1 (1),
pp 1-5.

DOI: 10.12691/iteces-1-1-1

Received November 26, 2013; Revised December 02, 2013; Accepted December 24, 2013

**Copyright:**© 2013 Science and Education Publishing. All Rights Reserved.

### Cite this article:

- Delshad, Majid, and Nima rakian. "A New ZCS High Step-up DC-DC Converter."
*International Transaction of Electrical and Computer Engineers System*1.1 (2013): 1-5.

- Delshad, M. , & rakian, N. (2013). A New ZCS High Step-up DC-DC Converter.
*International Transaction of Electrical and Computer Engineers System*,*1*(1), 1-5.

- Delshad, Majid, and Nima rakian. "A New ZCS High Step-up DC-DC Converter."
*International Transaction of Electrical and Computer Engineers System*1, no. 1 (2013): 1-5.

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### 1. Introduction

High step-up DC-DC converters are vastly used in green energy systems such as photovoltaic systems, fuel cell systems and etc. Modern DC-DC converters operate in high switching frequency to reduce their size and weight, but by increasing switching frequency, switching loss increases. To solve this problem, soft switching techniques are required [1-6]^{[1]}.

Quasi-resonant and resonant converters do not require any extra switch to provide soft switching conditions but these converters must be controlled by variable switching frequency which causes the complexity of control circuit and design of magnetic components ^{[7, 8, 9]}.

Using active clamp circuit is another technique to provide soft switching condition and absorbing voltage spike across the switch. Control of these converters is also pulse width modulation (PWM). Disadvantages of this technique are switch current stress, duty cycle losses and using extra switch ^{[10, 11, 12]}.

Furthermore, zero-voltage transition (ZVT) and zero-current transition (ZCT) are PWM controlled but for implementing of these converters, at least two switches are required ^{[13, 14, 15]}.

Although all the declared advantages exist on soft single switched converters, they usually have a large number of passive components, which increases conductors losses ^{[16, 17, 18]}.

In this paper a new boost PWM soft single switched converter without any auxiliary switch is introduced. In the proposed converter voltage and current stress does not increase significantly and additional components are not high. The switch is turned on under ZCS condition and turned off at almost ZVS. The proposed converter is PWM controlled therefore, the implementation of control circuit is simple. One of the advantages of this converter is the possibility of sharing the output power between the magnetic devices and operating at high power levels.

In this paper, the operation modes of the proposed converter are demonstrated in section II. In section III, the steady state analysis is presented. The Experimental result from a 100 watt prototype is presented in section IV to verify the theoretical analysis.

### 2. Circuit Configuration and Operation Principle of the Proposed Converter

**2.1. Circuit Description**

**Fig**

**ure**

**1.**The proposed step-up converter with auxiliary circuit

The proposed single switch converter is shown in Figure 1. Auxiliary circuit provides zero current switching (ZCS) condition at turn on and almost zero voltage switching (ZVS) at turn off for switch. S is the main switch and C_{b} is balancing capacitor. C_{1} and C_{2} are output capacitors and C_{r} is resonant capacitor. D_{1}-D_{3} are output diodes. In this convertor n and m are turns ratio of flyback and forward transformers respectively. Also L_{m1} and L_{m2 }are magnetizing inductance of flyback and forward transformers. L_{r1} and L_{r2} are coupled inductors in auxiliary circuit.

**2.2. Operation Principle**

In order to simplify the steady state analysis, the following assumptions are made.

All parasitic components are neglected.

The output capacitors are large enough, so these voltages are considered constant in a switching cycle.

The proposed circuit has five operating modes in one period. The key waveforms of the proposed converter are illustrated in Figure 2. The equivalent circuits for each operating interval are shown in Figure 3.

**Fig**

**ure**

**2.**The key waveforms of the proposed converter

Before the first mode, it is assumed that the switch is off and therefore diodes D_{1} and D_{2} are on and D_{3} is off and energy transfers to the output through flyback transformer.

**2.2.1. Mode1**

This mode begins when the switch S turns on under ZCS condition due to series inductor L_{r1}. The following equations are established:

(1) |

(2) |

(3) |

(4) |

This mode ends when I_{Sw }reaches I_{Lm2 }. Duration of this mode can be calculated by following equation:

(5) |

**2.2.2. Mode2**

When D_{2 }current reaches zero D_{3 }conducts under ZCS condition and also, L_{r1 }start to resonate with C_{r}. The resonant capacitor voltage and resonant inductor current are as following:

(6) |

(7) |

(8) |

(9) |

(10) |

Where

(11) |

(12) |

This mod ends when Vcr reaches zero. Duration of this mode is

(13) |

**2.2.3. Mode3**

When V_{cr} reaches zero this mode starts and D_{4} conducts under ZVS condition. C_{r} voltage is clamped at zero from this mode. Since the total ampere turns of L_{r1 }and L_{r2 }should stay constant.

(14) |

Furthermore, the L_{r1 }current is equal to the sum of the input current and L_{r2 }current, thus the following relations are obtained:

(15) |

(16) |

This mode ends when I_{in }reaches to I_{Lm1} and diode D_{1 }turns off.

**2.2.4. Mode4**

In this mod switch is turned off and C_{r }starts to charge in resonant fashion. By turning the switch off, D_{1} is turned on and the ampere turn of L_{r1 }transfer to L_{r2,} and now, the L_{r2 }ampere turn is the sum of its previous ampere turn plus the L_{r1 }ampere turn as described by

(17) |

(18) |

(19) |

(20) |

(21) |

**Fig**

**ure**

**3**

**.**Equivalent circuits for each operating interval of the proposed converter: (a):t

_{0}-t

_{1}, (b):t

_{1}-t

_{2}, (c):t

_{2}-t

_{3}, (d):t

_{3}-t

_{4}, (e):t

_{4}-t

_{0}, (The gray colored elements do not conduct current)

This mode ends when Vcr charges. Cr voltage can be calculated as following:

(22) |

**2.2.5. Mode5**

When L_{r2} current reaches zero diode D_{4} is turned off under ZCS condition. In this mode V_{cr}_{ }remains constant and similar to previous mode, magnetizing inductances discharge to the output.

### 3. Analysis of Proposed Converter

**3.1. Voltage dc Gain**

In this section, by writing volt-sec balance for flyback and forward transformers and writing KVL in output loop the following relations are obtained.

(23) |

(24) |

(25) |

Thus V_{C1}, V_{C2}, V_{Cb} are obtained from equations (26) to (28).

(26) |

(27) |

(28) |

Finally, the gain of proposed converter is calculated below:

(29) |

In Figure 4 the proposed converter gain compared with conventional boost converter . As seen in Figure 4, gain of proposed converter is higher than conventional isolated and non isolated boost converter.

**Fig**

**ure**

**4.**proposed converter gain compared with conventional boost converter versus duty cycle

3D plot of gain versus turn ratios and duty cycle is shown in Figure 5.

**3.2. Soft Switching Condition**

In this converter*, *L_{r1} provides ZCS condition for the switch turn on instant. This inductor can be chosen according to ^{[19]}, as follows

(30) |

**Fig**

**ure**

**5.**3D plot of gain versus turns ratio and duty cycle

Also, ZVS condition for the switch turn off instant is provided by C_{r}. Thus the value of this capacitor can be selected like snubber capacitors ^{[19]}, according to the following relation:

(31) |

Therefore, L_{r1} and Cr can be obtained from Figure 6 and Figure 7 versus various output power.

**Fig**

**ure**

**6.**L

_{r1 }value versus output power

**Fig**

**ure**

**7.**C

_{r}value versus output power

**3.3. Stress of Switching Devices**

The maximum voltage stress across the main switch and diodes can be obtained from (32) to (36).

(32) |

(33) |

(34) |

(35) |

(36) |

### 4. Experimental Results

The experimental results are presented in this section to verify the effectiveness of the proposed converter. The proposed converter specifications are listed in Table 1. Figure 8 and Figure 9 show the waveform of drain-source voltage, gate-source voltage and current of main switch to illustrate the ZCS feature. It can be observed that the main switch current is zero at the turn on instant. Also can be seen almost ZVS at turn off instant.

**Fig**

**ure**

**8.**

**Drain-source voltage and current (dashed) waveforms of main switch S (vertical scale 25V/div or 2.5A/div, time scale 1µs/div)**

**Fig**

**ure**

**9.**Drain-source voltage and current (dashed) waveforms of main switch S (vertical scale 25V/div or 2.5A/div, time scale 1µs/div)

### 5. Conclusion

In this paper, a new single soft switched isolated PWM converter is proposed. The flyback transformer which is connected to the output in series leads to high voltage gain and less voltage stress on the power devices. The auxiliary circuit contains two coupled inductors and one snubber capacitor. In this converter, switch is turned on under zero current switching and turn off under almost zero voltage switching. One of the main advantages of this converter is the possibility of sharing the output power between the magnetic devices and operating at high power levels. Switch is PWM controlled which simplifies the control implementation. The simulation results obtained from the proposed converter verifies the theoretical analysis.

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